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18w hi-fi amplifier and 35w driver description t he TDA2030 is a monolithic ic in pentawatt package intended for use as low frequency class ab amplifier. with vsmax=44v it is particularly suited for more reliable applications withou regulated supply and for 35w driver circuits using lowcost complementary pairs. t he TDA2030 provides high output current and has very low har m onic and c ro ss -o v er di s t or t ion. f ur t her t he de v i c e in c orpora t es a s hort c ir c uit pro t e c t ion s y s t em s o m pri s ing an arrange m ent f or au t o m a t i c ally li m i t ing t he di ss ipa t ed po w er t o as t o k eep t he w or k ing point of t he ou t put t ran s i s t ors w i t hin t heir s a f e opera t ing area. a c on v en t ional t her m al s y s t em is al s o in c luded. to-220 absolute maximum ratings (ta=25 c ) characteristics symbol value units supply voltage vs 22 v input voltage vi vs v differential input voltage vdi 15 v peak output current(internally limited) io 3.5 a total power dissipation at tcase=90 ptot 20 w storage temperature tstg -40~+150 c junction temperature tj -40~+150 c typical application tda203 0 1 2 3 5 4 vi +vs -vs c1 1 f c2 22 f c6 100 f c4 100nf c7 220nf c5 100nf c3 100 f d1 1n4001 d1 1n4001 r3 22k ? r1 22k ? r5 c8 r4 1 ? rl r3 680 ? tda203 0a 1
pin connection 1 non inverting input 2 inverting input 3 -vs 4 output 5 +vs electrical characteristics (refer to the test circuit,vs= 16v,ta=25 c ) parameter symbol test conditions min typ max unit supply voltage vs 6 22 v quiescent drain current id 50 80 ma input bias current ib 0.2 2 a input offset voltage vos vs= 22v 2 20 mv input offset current ios 20 200 na d=0.5%,gv=26db f=40to5khz output power po r l =8 ? 15 18 w r l =4 ? 10 12 w vs= 19v,r l =4 ? 13 16 w power bandwidth bw po=15w,r l =4 ? 100 khz slew rate sr 8 v/ sec open loop voltage gain gvo f=1khz 80 db closed loop voltage gain gvc 25.5 26 26.5 db total harmonic distortion d po=0.1 to 14w,r l =4 ? f=40 to 15khz 0.08 % po=0.1 to 14w,r l =4 ? f=1khz 0.03 % total harmonic distortion d po=0.1 to 9w,r l =8 ? f=40 to 15khz 0.05 % second order ccif intermodulation distortion d2 po=4w,r l =4 ? f2-f1=1khz 0.03 % third order ccif intermodulation distortion d3 f2=14khz, f1=15khz 0.08 % input noise voltage b=curve a 2 v input noise current b= 22hz to 22khz 3 10 v r l =4 ? ,rg=10k ? ,b=curve a signl to nois rtio s/n po=15w 106 db po=1w 94 db tda203 0 2
(continued) parameter symbol test conditions min typ max unit input resistance(pin 1) open loop,f=1khz 0.5 5 m ? supply voltage rejection r l =4 ? ,gv=26db r g = 2 2 ? ,f= 1 k h z 54 db thermal shut-down junction temperature 145 c test circuits TDA2030 1 2 3 5 4 vi +vs -vs c1 1 f c2 22 f c6 100 f c4 100nf c7 220nf c3 100nf c5 220 f d1 1n4001 d1 1n4001 r3 22k ? r1 13k ? r4 1 ? rl r3 680 ? tda203 0 3
TDA2030 1 2 3 5 4 vi +vs c7 220nf 0.1 f 1n4001 100k ? r4 1 ? rl=4 ? 4.7k ? 1n4001 100k ? 2.2 f 100k ? 2.2 f 100k ? 22 f 220 f 2200 f fig. 1 single supply amplifier tda203 0 4
10 2 10 3 10 4 10 5 10 6 10 7 10 1 -60 -20 20 60 100 140 phase gain gv (db) 180 90 0 phase fig.2 open loop frequency response 24 28 32 36 40 44 24 4 8 12 16 20 rl=4 ? rl=8 ? gv=26db d=0.5% f=40 to 15khz fig.3 output power vs. supply voltage fig.4 total harmonic distortion vs. output power fig.5 two tone ccif intermodulation distortion 10 -1 10 0 10 1 10 2 10 -2 10 -2 10 -1 10 0 10 1 10 2 vs=38v rl=8 ? vs=32v rl=4 ? f=15khz f=1khz gv=26db 10 1 10 2 10 -2 10 -1 10 0 10 1 10 2 10 3 10 4 10 5 order (2f1-f2) order (2f2-f1) vs=32v po=4w rl=4 ? gv=26db fig.6 large signal frequency response fig.7 maximum allowable power dissipation vs. ambient temperture 10 1 10 2 10 3 10 4 30 5 10 15 20 25 vs=15v rl=4 ? vs=15v rl=8 ? -50 0 50 100 150 200 30 5 10 15 20 25 i n f i n i t e h e a t s i n k h e a t s i n k h a v i n g r t y = 2 5 / w h e a t s i n k h a v i n g r t h = 4 / w h e a t s i n k h a v i n g r t h = 8 / w tamb ( ) ptot (w) frequency (khz) vo (vp-p) po (w) frequency (hz) po (w) vs (v) frequency (hz) po (w) d (%) d (%) tda203 0 5
tda203 0 1 2 3 5 4 vi +vs c3 0.22 f r3 56k ? rl=4 ? r4 3.3k ? 1n4001 c4 10 f r1 56k ? c1 2.2 f r2 56k ? c2 22 f c5 220 f /40v c8 2200 f r6 1.5 ? c6 0.22 f r5 30k ? r7 1.5 ? 1n4001 r8 1 ? c7 0.22 f bd908 bd907 f ig. 8 single s upply high po w er a m pli f ier( tda2032+bd908/bd907) typical performance of the circuit of fig. 8 parameter symbol test conditions min typ max unit supply voltage vs 36 44 v quiescent drain current id vs=36v 50 ma d=0.5%,r l =4 ? f=40hz to 15khz,vs=39v 35 output power po d=0.5%,r l =4 ? f=40hz to 15khz,vs=36v 28 w d=0.5%,f=1khz, r l =4 ? vs=39v 44 d=0.5%,r l =4 ? f=1khz,vs=36v 35 voltage gain gv f=1khz 19.5 20 20.5 db slew rate sr 8 v/ sec total harmonic d po=20w,f=1khz 0.02 % distortion po=20w,f=40hz to 15khz 0.05 % input sensitivity vi gv=20db,po=20w, f=1khz,r l =4 ? 890 mv signal to noise s/n r l =4 ? ,rg=10k ? b=curve a,po=25w 108 db ratio r l =4 ? ,rg=10k ? b=curve a,po=25w 100 tda203 0 6
24 28 32 34 36 40 5 15 25 35 45 fig. 10 output power vs. supply voltage po (w) vs (v) 10 -1 10 0 10 1 10 -2 10 -1 10 0 f=15khz f=1khz vs=36v rl=4 ? gv=20db d (%) po (w) fig. 11 total harmonic distortion vs. output power 100 250 400 550 700 0 5 10 15 20 gv=26db gv=20db vi (mv) po (w) fig. 12 output power vs. input level 0 5 10 15 20 0 8 16 24 32 po (w) ptot (w) complete amplifier bd908/ bd907 utc2030a fig. 13 power dissipation vs. output power tda203 0 1 2 3 5 4 vi +vs -vs c1 1 f c2 22 f c6 100 f c4 100nf c7 220nf c3 100nf c5 100 f d1 1n4001 d2 1n4001 r3 22k ? r1 22k ? r5 c8 r4 1 ? rl r3 680 ? fig. 14 typical amplifier with split power supply tda203 0 7
TDA2030 TDA2030 c1 220 f c6 100 f c7 100nf 1 2 3 5 4 1 2 3 4 5 c8 0.22 f c4 22 f c9 0.22 f c5 22 f c3 100nf c2 100 f r2 22k ? r5 22k ? r6 680 ? r9 1 ? r8 1 ? r4 680 ? r3 22k ? r7 22k ? r1 22k ? vs+ vs- in rl 8 ? fig. 16 bridge amplifier with split power supply(po=34w,vs+=16v,vs-=16v) multiway speaker systems and active boxes multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is speciailly designed and optimizied to handle a limited range of frequencies.commonly,these loudspeaker systems divide the audio spectrum two or three bands. to maintain a flat frequency response over the hi-fi audio range the bands cobered by each loudspeaker must overlap slightly.imbalance between the loudspeakers produces unacceptable results therefore it is important to ensure that each unit generates the correct amount of acoustic energy for its segmento of the audio spectrum.in this respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies of the crossover filters(see fig. 18).as an example,1 100w three-way system with crossover frequencies of 400hz and 3khz would require 50w for tthe woofer,35w for the midrange unit and 15w for the tweeter. both active and passive filters can be used for crossovers but active filters cost significantly less than a good passive filter using aircored inductors and non-electrolytic capacitors.in addition active filters do not suffer from the typical defects of passive filters: --power less; --increased impedance seen by the loudspeaker(lower damping) --difficuty of precise design due to variable loudspeaker impedance. tda203 0 8
obviously, active crossovers can only be used if a power amplifier is provide for each drive unit.this makes it particularly interesting and economically sound to use monolithic power amplifiers. in some applications complex filters are not realy necessary and simple rc low-pass and high-pass networks(6db/octave) can be recommended. the result obtained are excellent because this is the best type of audio filter and the only one free from phase and transient distortion. the rather poor out of band attenuation of single rc filters means that the lodspeaker must operate linearly well beyond the crossover frequency to avoid distortion. a more effective solution,named "active power filter" by sgs is shown in fig. 19. the proposed circuit can realize combined power amplifiers and 12db/octave or 18db octave high-pass or low- pass filters. in practive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active filter operations. the impedance at the pin(-) is of the order of 100 ? ,while that of the pin (+) is very high, which is also what was wanted. 10 2 10 3 10 4 10 5 10 1 0 20 100 40 60 80 morden music spectrum iec/din noise spectrum for speaker testing fig. 18 power distribution vs. frequency vs+ vs- 3.3k ? 100 ? r2r1 c1 c2 c3 rl fig. 19 active power filter r3 the components values calculated for fc=900hz using a bessel 3rd sallen and key structure are: c1=c2=c3=22nf,r1=8.2k ? ,r2=5.6k ? ,r3=33k ? . using this type of crossover filter, a complete 3-way 60w active loudspeaker system is shown in fig. 20. it employs 2nd order buttherworth filter with the crossover frequencies equal to 300hz and 3khz. the midrange section consistors of two filters a high pass circuit followed by a low pass network.with vs=36v the output power delivered to the woofer is 25w at d=0.06%( 30w at d=0.5%).the power delivered to the midrange and the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance(rl=4 ? to 8 ? ). it is quite common that midrange and tweeter speakers have an efficiency 3db higher than woofers. musical instruments amplifiers another important field of application for active system is music. in this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it is also more reliable. a typical example(see fig. 21) consist of four amplifiers each driving a low-cost, 12 inch loudspeaker. this application can supply 80 to 160w rms. tda203 0 9
transient inter-modulation distortion(tim) transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers. when a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation distortion will be produced as in fig.22.since transients occur frequently in music this obviously a problem for the designed of audio amplifiers. unfortunately, heavy negative feedback is frequency used to reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient inter-modulation(tim situation.)the best known 1 2 5 4 3 tda203 0 1 2 5 4 3 tda203 0 1 2 5 4 3 tda203 0 0.22 f 2200 f 18nf 33nf 100 f 0.22 f 1n4001 1 f 0.1 f 0.1 f 0.22 f vs+ 18nf 3.3nf 100 f 0.22 f 0.1 f 0.1 f 47 f 0.22 f 100 0.22 f 220 1n4001 bd908 bd907 22k ? 1.5 ? 1.5 ? 3.3k ? 22k ? 22k ? 680 ? 100 ? 1 ? 22k ? 22k ? 6.8k ? 3.3k ? 100 ? 2.2k ? vs+ 1n4001 1n4001 1n4001 1 ? 2.2k ? 12k ? 100 ? 22k ? 22k ? 22k ? vs+ 100 f in high-pass 3khz high-pass 3khz band-pass 300hz to 3khz low-pass 300hz 1n4001 tda203 0 10
20 to 40w amplifier 20 to 40w amplifier 20 to 40w amplifier 20 to 40w amplifier pre amplifier power amplifier feedback path input v1 v2 v3 v4 v4 output v1 v2 v3 v4 fig.21 high power active box for musical instrument fig.22 overshoot phenomenon in feedback amplifiers method for the measurement of tim consicts of feeding sine waves superimposed onto square wavers,into the amplifier under test.the output spectrum is then examined using a spectrum analyser and compared to the input.this method suffers from serious disadvantages:the accuracy is limited, the measurement is a tather delicate operation and an expensive spectrum analyser is essential.a new approach (see technical note 143(applied by sgs to monolithic amplifiers measurement is fast cheap,it requires nothing more sophisticated than an oscilloscope-and sensitive-and it can be used down to the values as low as 0.002% in high power amplifiers. the "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20khz sawtooth waveform.the amplifier has no difficulty following the slow ramp but it cannot follow the fast edge.the output will follow the upper line in fig.23 cutting of the shade area and thus increasing the mean level.if this output signal is filtered to remove the sawtooth,direct voltage remains which indicates the amount of tim distortion, although it is difficult to measure because it is indistingishable from the dc offset of the amplifier.this problem os neatly avoided in the is-tim method by periodically inverting the sawtooth waveform at a low audio frequency as shown in fig.24.inthe case of the sawtooth in fig. 25 the means level was increased by the tim distortion, for a sawtooth in the other direction the opposite is ture. m2 m1 sr(v/ s) input signal filtered output siganal fig.23 20khz sawtooth waveform fig.24 inverting sawtooth waveform tda203 0 11
the result is an ac signal at the output whole peak-to-peak value is the tim voltage,which can be measured easily with an oscilloscope.if the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are measured,the tim can be found very simply from: tim vout vsawtooth * 100 = 10 -1 10 0 10 1 10 2 10 -2 10 -1 10 0 10 1 TDA2030 bd908/907 gv=26db vs=36v rl=4 ? rc filter fc=30khz fig. 25 tim distortion vs. output power po(w) tim(%) 10 -1 10 0 10 1 10 2 vo(vp-p) 10 -1 10 0 10 1 10 2 rc filter fc=30khz fig. 26 tim design diagram(fc=30khz) ti m= 0 . 1 % ti m=0 . 0 1 % t i m = 1% sr(v/ s) i n f ig . 25 t he e x peri m en t al re s ul t s are s ho w n f or t he 30w a m pli f ier u s ing t he tda203 0a as a driver and a low-cost complementary pair.a simple rc filter on the input of the amplifier to limit the maxmium signal slope(ss) is an effective way to reduce tim. the digram of fig.26 originated by sgs can be used to find the slew-rate(sr) required for a given output power or voltage and a tim design target. for example if an anti-tim filter with a cutoff at 30khz is used and the max.peak to peak output voltage is 20v then, referring to the diagram, a slew-rate of 6v/ s is necessary for 0.1% tim. as shown slew-rates of above 10v/ s do not contribute to a further reduction in tim. slew-rates of 100v/ s are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to turn the amplifier into a radio receiver. power supply using monolithic audio amplifier with non regulated supply correctly.in any working case it must provide a supply voltage less than the maximum value fixed by the ic breakdown voltage. it is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage v aria t ions w i t h and w i t hout load . t he tda203 0a(vsmax=44v) is particularly suitable for substitution of the standard ic power amplifiers(with vsmax=36v) for more reliable applications. an example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram of fig.27. a regulated supply is not usually used for the power output stages because of its dimensioning must be done taking into account the power to supply in signal peaks.they are not only a small percentage of the total music signal, with consequently large overdimensioning of the circuit. even if with a regulated supply higher output power can be obtained(vs is constant in all working conditions),the additional cost and power dissipation do not usually justify its use.using non-regulated supplies,there are fewer designe restriction.in fact,when signal peaks are present, the capacitor filter acts as a flywheel supplying the required energy. tda203 0 12
in average conditions,the continuous power supplied is lower.the music power/continuous power ratio is greater in case than for the case of regulated supplied,with space saving and cost reduction. 0 0.4 0.8 1.2 1.6 2.0 28 30 32 34 36 vo(v) io(a) fig.27 dc characteristics of 50w non-regulated supply vo 3300 f 220v 0 2 4 ripple (vp-p) ripple vout mains(220v) secondary voltage dc output voltage(vo) io=0 io=0.1a io=1a +20% 28.8v 43.2v 42v 37.5v +15% 27.6v 41.4v 40.3v 35.8v +10% 26.4v 39.6v 38.5v 34.2v 24v 36.2v 35v 31v -10% 21.6v 32.4v 31.5v 27.8v -15% 20.4v 30.6v 29.8v 26v -20% 19.2v 28.8v 28v 24.3 short circuit protection t he tda203 0a has an original circuit which limits the current of the output transistors.this function can be c on s idered as being peak po w er li m i t ing ra t her t han s i m ple c urrent li m i t ing . i t redu c es t he po s s ibili t y t hat t he de v i c e ge t s da m aged during an a c c iden t al s hort c ir c uit f rom ac ou t put t o ground. thermal shut-down the presence of a thermal limiting circuit offers the following advantages: 1).an overload on the output (even if it is permanent),or an above limit ambient temperture can be easily supported since the tj can not be higher than 150 2).the heat-sink can have a smaller factor of safety compared with that of a convential circuit,there is no possibity of device damage due to high junction temperature increase up to 150, the thermal shut-down simply reduces the power dissipation and the current consumption. tda203 0 13
application suggestion the recommended values of the components are those shown on application circuit of fig.14. different values can be used.the following table can help the designer. component recommended value purpose large than recommended value large than recommended value r1 22k ? closed loop gaon setting. increase of gain decrease of gain r2 680 ? closed loop gaon setting. decrease of gain increase of gain r3 22k ? non inverting input biasing increase of input impedance decrease of input impedance r4 1 ? frequency stacility danger of oscillation at high frequencies with inductive loads. r5 3r2 upper frequency cutoff poor high frequencies attenuation dange of oscillation c1 1 f input dc decoupling increase of low frequencies cutoff c2 22 f inverting dc decoupling increase of low frequencies cutoff c3,c4 0.1 f supply voltage bypass dange of oscillation c5,c6 100 f supply voltage bypass dange of oscillation c7 0.22 f frequency stability larger bandwidth c8 1/(2 *b*r1) upper frequency cutoff smaller bandwidth larger bandwidth d1,d2 1n4001 to protect the device against output voltage spikes. tda203 0 14

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